By Warren L. Stutzman

ISBN-10: 0471025909

ISBN-13: 9780471025900

Hugely revered authors have reunited to replace the well-known 1981 version that's nonetheless hailed as the most effective in its box. This variation comprises fresh antenna strategies and functions. It contains a succinct remedy of the finite distinction, time area (FDTD) computational approach. it's also the 1st textual content to regard actual thought of diffraction (PTD).

**Read or Download Antenna Theory and Design, 2nd Edition PDF**

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**Extra resources for Antenna Theory and Design, 2nd Edition**

**Sample text**

Z)2 . 2 ()rA + cos () sm . () aA) =--2 - 51 (sm f3 4'1T r (1-77) Note that this power density vector is imaginary and therefore has no time-average radial power flow. The radiation fields, in contrast, are in-phase giving a real-valued Poynting vector that is radially directed; see (1-72) and (1-74). The imaginary power density corresponds to standing waves, rather than traveling waves associated with radiation, and indicate stored energy as in any reactive device. The quadrature phase relationship between the electric and magnetic field components of (1-76) 24 Chapter 1 Antenna Fundamentals and Definitions indicates that energy is interchanged between these fields with time.

Substituting 6 = 90° in (1-114) gives unity and we see that F(6) is properly normalized. In general, a normalized field pattern can be written as the product I F(6, c/J) = gee, c/J )f(6, c/J) I (1-115) where g(6, c/J) is the element factor and f(6, c/J) the pattern factor. The pattern factor comes from the integral over the current and is strictly due to the distribution of current in space. The element factor is the pattern of an infinitesimal current element in the current distribution. For example, we found for a z-directed current element that F(6) = sin 6.

If {3r » 1, the second term is small compared to the first and can be neglected, as we did for the far-field approximation of the ideal dipole in Sec. 6. f, (1-91) f JL 41Tr JL z The electric field is found from (1-47), which is E = -jwA _ j V(V . A) WJLE Using (1-78) in (1-79) and retaining only the r- 1 term (and assuming f3r to the far-field approximation (1-92) » 1) lead (1-93) 28 Chapter 1 Antenna Fundamentals and Definitions Note that this result is the portion of the first term of (1-92) that is transverse to r because -jwA = -jw( -A z sin 00 + A z cos Or).

### Antenna Theory and Design, 2nd Edition by Warren L. Stutzman

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